Radio frequency tuner

ABSTRACT

A RF tuner is described for handling RF signals in a broad frequency range and a broad power range while maintaining high linearity and tolerating high power blockers. A continuous feedback loop comprising a substantially linear LNA and a radio frequency RSSI can adjust the power of the RF signal on the RF side. On the IF side, a continuous feedback loop comprising a substantially linear, variable gain transconductor and a RSSI can adjust the power of the IF signal.

CLAIM OF PRIORITY

This application is a continuation of U.S. patent application Ser. No.12/711,218 entitled “RADIO FREQUENCY TUNER,” filed on Feb. 23, 2010,which claims priority to U.S. Provisional Patent Application No.61/250,543 entitled “ARCHITECTURE AND CONFIGURATION FOR THE RF TVTUNER,” filed on Oct. 11, 2009.

COPYRIGHT NOTICE

A portion of the disclosure of this patent document contains materialwhich is subject to copyright protection. The copyright owner has noobjection to the facsimile reproduction by anyone of the patent documentor the patent disclosure, as it appears in the Patent and TrademarkOffice patent file or records, but otherwise reserves all copyrightrights whatsoever.

FIELD OF THE INVENTION

This invention relates generally to the field of radio frequencyreceivers, and more specifically to amplification of radio frequencysignals in tuners.

BACKGROUND

In the age of information technology, the requirements of communicationssystems are increasing at a staggering pace. The receiver is a keycomponent in the performance of communication systems. Its function isto receive incoming signals and process the signals so they can be usedby other components in the device. Devices such as cell phones, PDAs,mobile televisions, personal navigation devices, personal media players,and a myriad others contain receivers that perform this function.Signals can be conveyed to a receiver via an antenna, through directwire transmission, and in other ways.

Ideally, a receiver needs to produce a signal of sufficiently high powerthat contains undistorted desirable components, such as the preferredchannel, and none of the undesirable components, such as blockers,adjacent channels, and noise. Generally, signals are optimized for thesetraits in a portion of the receiver called a tuner. Building a powerefficient, inexpensive, and compact tuner that meets industry standardscan be extremely challenging for manufacturers.

First, an incoming signal's power may vary significantly and fluctuaterapidly due to, for example, attenuation, variation in distance betweenthe receiver and the transmitter, fading, and the Doppler Effect. Signalpower fluctuations may be in the order of several magnitudes. Hence, atuner must be capable of performing a broad range of amplification whilepreserving other signal characteristics. Second, the gain of undesiredcomponents can be as much as several orders of magnitude larger than thedesired signal and can be located near the desirable channel in thefrequency range, for instance, in the case of near adjacent channels.Sharp, selective filtering is required to reject such components. Inaddition, tuners need to perform in a broad frequency range, such as thebroadband TV signal range of 50 MHz-1 GHz, while maintaining a highrequired signal to noise ratio (SNDR), particularly in TV applications.These problems present significant challenges in integration of RFtuners.

To achieve these goals, existing devices employ CAN tuners, which arelarge and limited in application. Current solid-state tuners are basedon external SAW filters, which are expensive, consume a lot of power,and usually are not applied in inexpensive CMOS technology. What isneeded is a highly integrated RF tuner that is compact in size,inexpensive to produce, and exhibits low power consumption.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows an example of a RF receiver in accordance with variousembodiments.

FIG. 2 shows an example of an amplifier stage in a RF tuner, inaccordance with various embodiments of the invention.

FIG. 3 shows an example of a buffer comprising an adjustable,substantially linear attenuator, in accordance with one embodiment.

FIG. 4 shows an example of an attenuator that can be contained in abuffer, in accordance with various embodiments.

FIG. 5 is a flow-chart illustration of the process of RF signalamplification in a RF tuner, in accordance with various embodiments ofthe invention.

FIG. 6 shows an example of a power detector, in accordance with variousembodiments.

FIG. 7 shows an example of a radio frequency RSSI in accordance with oneembodiment.

FIG. 8 shows an example of a control signal generator in accordance withvarious embodiments.

FIG. 9 shows an example of a configuration of components for downconverting a RF signal and fixing the power of a produced low frequencysignal, in accordance with various embodiments of the invention.

FIG. 10 is a flow-chart illustration of the process of down converting aRF signal and fixing the power of a produced low frequency signal, inaccordance with various embodiments of the invention.

FIG. 11 shows an example of a transconductor comprising a substantiallylinear attenuator in accordance with various embodiments.

FIG. 12 shows an example of a RF tuner with a portion where RF signalsin a broad range of powers can be amplified to produce RF signals of afixed preferred power and a portion where RF signals can be downconverted, filtered to remove undesired components, and amplified toproduce a low frequency signal with a fixed preferred power, inaccordance with one embodiment.

DETAILED DESCRIPTION

In the following description, numerous specific details are set forth inorder to provide a thorough understanding of the present invention.However, it will be apparent to one skilled in the art that the presentinvention can be practiced without these specific details. In otherinstances, well known circuits, components, algorithms, and processeshave not been shown in detail or have been illustrated in schematic orblock diagram form in order not to obscure the present invention inunnecessary detail. Additionally, for the most part, details concerningcommunication systems, transmitters, receivers, communication devices,and the like have been omitted inasmuch as such details are notconsidered necessary to obtain a complete understanding of the presentinvention and are considered to be within the understanding of personsof ordinary skill in the relevant art. It is further noted that, wherefeasible, all functions described herein may be performed in eitherhardware, software, firmware, analog components or a combinationthereof, unless indicated otherwise. Certain terms are used throughoutthe following description and Claims to refer to particular systemcomponents. As one skilled in the art will appreciate, components may bereferred to by different names. This document does not intend todistinguish between components that differ in name, but not function. Inthe following discussion and in the Claims, the terms “including” and“comprising” are used in an open-ended fashion, and thus should beinterpreted to mean “including, but not limited to . . . . ”

Embodiments of the present invention are described herein. Those ofordinary skill in the art will realize that the following detaileddescription of the present invention is illustrative only and is notintended to be in any way limiting. Other embodiments of the presentinvention will readily suggest themselves to such skilled persons havingthe benefit of this disclosure. Reference will be made in detail toimplementations of the present invention as illustrated in theaccompanying drawings. The same reference indicators will be usedthroughout the drawings and the following detailed description to referto the same or like parts.

In the interest of clarity, not all of the routine features of theimplementations described herein are shown and described. It will, ofcourse, be appreciated that in the development of any such actualimplementation, numerous implementation-specific decisions must be madein order to achieve the developer's specific goals, such as compliancewith applications and business-related constraints, and that thesespecific goals will vary from one implementation to another and from onedeveloper to another. Moreover, it will be appreciated that such adevelopment effort might be complex and time-consuming, but wouldnevertheless be a routine undertaking of engineering for those ofordinary skill in the art having the benefit of this disclosure.

Further, in this specification and Claims, it is to be understood that“amplification” can refer to increasing a signal's gain in the case ofpositive amplification, and to decreasing a signal's gain, orattenuation, in the case of negative amplification. Hence, the term“attenuation” can be interchangeable with the term “amplification” butfor the sake of simplicity only one of the terms “amplification” or“attenuation” is used throughout the specification and either termshould be understood to encompass both meanings.

In various embodiments, systems and methods are described for handlingRF signals in a RF receiver. A RF signal can be received in a portion ofthe receiver referred to as the RF tuner. The RF tuner can receive a RFsignal from an antenna, hard wire, or other means and produce a lowfrequency signal, such as a baseband or an intermediate frequency (IF)signal. For example, the received RF signal can be a broadband TV signalin UHF and VHF frequencies. The produced signal can be an IF signal oran IF in-phase (I) signal component and an IF quadrature-phase (Q)signal component.

FIG. 1 shows an example of a RF receiver in accordance with variousembodiments. A RF signal can be received in an antenna 101 and conveyedto a RF receiver 100. In the RF receiver 100, the signal can be conveyedto a RF tuner 102. In the RF tuner 102, the signal can be amplified inamplifier stages with adjustable level of gain 108. The level ofamplification in the amplifier stage 108 can be adjusted based on ameasured power of the signal, such as in a continuous feedback loop, toproduce a signal of a fixed desired power. After amplification in theamplifier stage 108, the signal can be conveyed to a band-pass filter103 to filter out undesirable signal components such as blockers. Afterthe band-pass filter 103, the signal can be conveyed to a transconductorwith adjustable level of amplification 109 to transform the signal fromvoltage to current and adjust the signal's gain. The level ofamplification in the transconductor 109 can be adjusted based on ameasured power of the signal, such as in a continuous feedback loop, toproduce a signal of a fixed desired power. After the transconductor 109,the signal can be conveyed to a mixer 104, where the signal can be downconverted to a low frequency, such as intermediate frequency. After themixer 104, the signal can be conveyed to a filter stage 105, to filterout high and/or low undesired frequencies. From the tuner 102, thesignal can be conveyed to an analog to digital converter (ADC) 106 toconvert the signal to the digital domain. The digital signal can then beconveyed from the RF receiver 100 to a digital demodulator 107, where itcan be processed further before being conveyed to other portions of thedevice.

The RF signal received at the tuner 102 can contain undesired signalcomponents such as blockers, adjacent channels, and/or noise. The gainof undesired blockers can be orders of magnitude larger than the desiredsignal and can be located near the desirable channel in the frequencyrange, for instance, in the case of near adjacent channels. Sharp,selective filtering can be utilized to reject such blockers. Inaddition, tuners may need to perform in a broad frequency range, such asthe broadband TV signal range of 50 MHz-1 GHz, while maintaining a highrequired signal to noise ratio (SNDR), particularly in TV applications.These problems present significant challenges in integration of RFtuners.

Further, an incoming signal's power may vary significantly and fluctuaterapidly due to, for example, attenuation, variation in distance betweenthe receiver and the transmitter, fading, and the Doppler Effect. Signalpower fluctuations may be in the order of several magnitudes. Hence, itcan be advantageous for a tuner to perform a broad range ofamplification while preserving other signal characteristics. As will beseen, the embodiments described herein provide such a tuner platform inan elegant manner.

To achieve these goals, existing devices employ CAN tuners, which arelarge and limited in application. Further, current solid-state tunersare based on external SAW filters, which are expensive, consume a lot ofpower, and usually are not applied in cost-effective CMOS technology.According to the invention, systems and methods are provided herein foran architecture that can allow construction of highly integrated,compact, inexpensive, and power efficient tuners that can be employed inCMOS technology.

For example, according to one embodiment, high-power blockers, high SNDRrequirements, and a high dynamic range of input signal power posessignificant challenges for TV tuners developed in sub-micron CMOSprocess technology. High-power blockers introduce non-linearity into asignal when the blockers pass through each stage of the tuner. Forexample, in a received RF signal containing a 0 dBm adjacent channelcomponent and a −20 dBm desired signal component, to meet a 40 dB SNDRrequirement, the nonlinearity components introduced by the adjacentchannel passing through tuner stages must be kept below −60 dBm (−20 ddBm−40 dB=−60 dBm), which can be challenging, especially in sub-micronCMOS process technology. Further, since a signal may need to beattenuated and filtered, all the tuner stages, including attenuationstages and filtering stages, should meet this linearity requirement.Moreover, to meet industry requirements, any solution should be costeffective and compact.

According to one embodiment, the challenges of RF tuners can beaddressed by employing multi-stage amplification and filtering withcontinuous and substantially linear power level control in each stage.Different stages can be employed for attenuating near and/or farblockers while preserving noise performance and achieving desirablesignal gain. Multi-stage amplification and filtering can also bedesirable in amplifying low power signals and signals close to thesensitivity power level of the tuner. Far blockers can be removed in aband-pass filter (BPF), while near blockers can be attenuated after downconversion. Further, a bypass mode can be considered for high inputpower signals, such as signals three to four orders of magnitude higherin power than the tuner's sensitivity level. In order to keep a requiredSNDR, signal and blocker power can be estimated in each stage and thegain on the respective RF path can be adjusted continuously; forexample, through feedback loops.

In various embodiments, the power of the signal at the input to theband-pass filter 103 can be fixed at a preferred value by controllingthe amplification of the RF signal in the amplification stage 108. Forexample, a feedback loop can be utilized that measures signal power atthe input of the band-pass filter 103 and adjusts amplification in theamplifier stage 108 accordingly. Far blockers can be removed in theband-pass filter 103.

Further, the power of the received RF signals at the RF tuner 102 canvary by as much as several magnitudes, hence, a system that amplifiesincoming signals to produce signals of a fixed power can be configuredfor amplifying signals in a wide range of incoming powers. With this inmind, in various embodiments, a received RF signal can be amplified in aset of components with a large range of adjustable amplification, thepower of the signal after amplification can be measured, and the levelof amplification in the set of components can be adjusted to fix thepower of the signal at a preferred power value. As will be describedbelow, the level of amplification in the set of components can beadjusted continuously using systems such as continuous feedback loopsand/or multiple, selectable amplification paths.

In various embodiments, an amplifier stage, such as the amplifier stage108 of FIG. 1, can comprise low noise amplifiers (LNAs) and/or bufferswith adjustable levels of amplification and/or attenuation. The amountof amplification of the RF signal in the LNAs and/or buffers can becontrolled through continuous feedback loops. A continuous feedback loopcan comprise a unit that measures signal power, which measurement can becontinuous, and a unit that adjusts the amplification and/or attenuationin the LNAs and/or buffers based on the measured signal power accordingto defined executable logic contained in the device, which adjustmentcan be continuous.

Further, the amplification in the amplifier stage can be adjusted byconveying the RF signal down one of a multiple amplification paths,wherein each amplification path can produce a different amount ofamplification and/or attenuation of the RF signal. Any of the multipleamplification paths can contain LNAs and/or buffers, which LNAs andbuffers can be adjustable in a feedback loop. The multiple amplificationpaths can contain continuous feedback loops to adjust amplificationand/or attenuation of the RF signal in LNAs and/or buffers on the path.

FIG. 2 shows an example of an amplifier stage in a RF tuner, inaccordance with various embodiments of the invention. The amplifierstage 108 in FIG. 1 can include components as described in the exampleof FIG. 2. In the example illustrated, an incoming RF signal 202 can beconveyed down a main path 200 or a bypass path 201. The incoming RFsignal 202 conveyed to a first LNA 204 on the main path 200 or a firstLNA 207 on the bypass path 201 can be single ended or differential.After the first LNAs 204, 207, the signal can be differential.

Initially, the signal can be conveyed down the main path 200, which canbe configured to optimize amplification of low power signals, such assignals of power lower than −30 dBm, for signal characteristics such asnoise figure and linearity. A first power detector (PD1) 209 can measurethe power of the signal after it is amplified in the first LNA 204 toproduce a first power value, P1. An example of such a power detectorwill be described in further detail in FIG. 6. The power value P1 can beconveyed to a bypass controller 213 where a decision can be made, basedon the value P1, to convey further incoming RF signals 202 down thebypass path 201, which bypass path 201 can produce less amplification ofthe RF signal than the main path 200. The bypass path 201 can beconfigured to optimize amplification of high power signals, such assignals of power higher than −20 dBm, for signal characteristics such asnoise figure and linearity. In this case, the bypass controller 213 cansend a signal to close the switch 203 and thereby convey subsequentincoming RF signals 202 down the bypass path. For example, the bypasscontroller 213 may compare P1 to a first threshold value, T1. In anembodiment, if P1 is higher than T1, then the bypass controller 213 canswitch amplification to the bypass path 201. In various embodiments, tostabilize the system, the logic incorporated into the bypass controller213 can delay switching amplification paths and/or use averages of P1instead of single measurements. For instance, in various embodiments,the bypass controller 213 can switch amplification to the bypass path ifthe average value of P1 over a predefined time period or for apredefined number of measurements is higher than T1. In otherembodiments, switching may be delayed until a predefined number ofmeasurements, out of a total number of measurements of P1, are higherthan T1.

In the figure, the bypass switch 203 is intended to illustrate thefunction that incoming RF signals 202 will be conveyed down the bypasspath and not the main path 200 when the switch 203 is in the closedposition. It will be apparent, to one skilled in the art, that other andadditional means may be used to activate the preferred path anddeactivate the un-preferred path, such as having switches on both pathsand/or powering up and powering down components on the preferred andun-preferred paths.

With the incoming RF signal 202 routed to the bypass path, amplificationcan be performed in the first 207 and second 208 LNAs. In variousembodiments, the first LNA 207 can be an adjustable LNA producing gainthat can be varied from 0 to −30 dB, and the second LNA 208 can produce10 dB gain. After amplification, the signal power can be measured in asecond power detector (PD2) 210 to derive a second power value P2. Anexample of such a power detector will be described in further detail inFIG. 6. The power value can be conveyed to the digital bypass controller213 where a decision can be made, based on the value P2, to conveyfurther incoming RF signals 202 down the main path 200. In which case,the bypass controller 213 can send a signal to open the switch 203 andthereby convey subsequent incoming RF signals 202 down the main path.For example, the bypass controller 213 can compare P2 to a secondthreshold value, T2. In an embodiment, if P2 is lower than T2, then thebypass controller 213 can switch amplification to the main path 200. Invarious embodiments, to stabilize the system, the logic incorporatedinto the bypass controller 213 can delay switching amplification pathsand/or use averages of P2 instead of single measurements. For instance,in various embodiments, the bypass controller 213 can switchamplification to the main path if the average value of P2 over apredefined time period or for a predefined number of measurements islower than T2. In other embodiments, switching can be delayed until apredefined number of measurements, out of a total number of measurementsof P2, are lower than T2.

The threshold values T1 and T2 can be set to introduce more stabilityinto the system. For example, T1 and T2 can be set to create an incomingsignal power hysteresis in the system. Namely, the values T1 and T2 canbe chosen so that amplification is switched to the bypass path forincoming signals of higher power than the incoming signals for whichamplification is switched back to the main path. An advantage of thisembodiment is that incoming signals that produce power measurements thatfluctuate around one of the threshold values will not cause the systemto rampantly switch between routines thereby creating instability. Forexample, in various embodiments, the value of T1 can be in the range of−15 dBm to −5 dBm, for instance, −10 dBm. In various embodiments, T2 canbe in the range of −35 dBm to −25 dBm, for example, −30 dBm.

In various embodiments, with amplification of the RF signal beingperformed on the main path 200, the amount of amplification in the LNAson the main path 200 can be adjusted using a continuous feedback loop.For example, in various embodiments, after amplification in the first204, a second 205, and a third 206 LNA, the signal can be conveyed to athird power detector (PD3) 218 and then to an RF RSSI 215. The signalpower can be measured in the power detector 218 and the power valuesignal can be conveyed to the RF RSSI 215. An example of such a powerdetector will be described in further detail in FIG. 6. The power of thesignal produced on the main path 200 can be controlled by adjusting theamount of amplification in the second LNA 205 based on the measuredsignal power according to executable logic incorporated in the RF RSSI215, the adjustment of amplification can be performed continuously. Inan embodiment, the signal power can be measured using continuouswideband RF power measurement. The power detector 218 can be located inthe RF RSSI 215 or the power detector 218 can be a separate componentfrom the RF RSSI 215. Hence, in various embodiments, the RF RSSI 215 canbe configured so that the power of the signal produced on the main path200 is a determined, fixed preferred value. For example, the continuousfeedback loop can be configured so that the determined preferred valueof the signal power after amplification on the main path 200 is −20 dBm.In that case, if the RF RSSI 215 measures that the power of the producedsignal is −15 dBm, the RSSI can send a signal to the adjustable LNA 205to decrease amplification in the adjustable LNA 205 by 5 dB. Similarly,if the RF RSSI 215 measures that the produced signal's power is −25 dBm,the RF RSSI 215 can send a signal to the adjustable LNA 205 to increaseamplification in the adjustable LNA 205 by 5 dB. In various embodiments,the RF RSSI 215 can be configured so that the determined preferred powervalue of the signal produced on the main path 200 in the continuousfeedback loop can be changed. For example, either through user input orthrough a decision made by logic incorporated in the device, thedetermined preferred power value of the signal after amplification onthe main path 200 in the device of the above example may be changed to−18 dBm instead of −20 dBm. In various embodiments, the determinedpreferred power value of the signal can be programmable through serialports in the RF RSSI 215 through a SPI or an I2C protocol.

In various embodiments, with amplification of the RF signal beingperformed on the bypass path 201, the amount of amplification in theLNAs on the bypass path 201 can be adjusted using a continuous feedbackloop. For example, in various embodiments, after amplification in thefirst 207 and second 208 LNAs, the signal can be conveyed to a thirdpower detector (PD3) 218 and then to a RF RSSI 215. The signal power canbe measured in the power detector 218 and the power value signal can beconveyed to the RF RSSI 215. An example of such a power detector will bedescribed in further detail in FIG. 6. The power of the signal producedon the main path 200 can be controlled by adjusting the amount ofamplification in the second LNA 205 based on the measured signal poweraccording to executable logic incorporated in the RF RSSI 215, theadjustment of amplification can be performed continuously. In anembodiment, the signal power can be measured using continuous widebandRF power measurement. The power detector 218 can be located in the RFRSSI 215 or the power detector 218 can be a separate component from theRF RSSI 215. Hence, in various embodiments, the RF RSSI 215 can beconfigured so that the power of the signal produced on the bypass path201 is a determined preferred value. For example, the continuousfeedback loop can be configured so that the determined preferred valueof the signal power after amplification on the bypass path 201 is −20dBm. In that case, if the RF RSSI 215 measures that the producedsignal's power is −15 dBm, the RSSI can send a signal to the adjustableLNA 207 to decrease amplification in the adjustable LNA 207 by 5 dB.Similarly, if the RF RSSI 215 measures that the produced signal's poweris −25 dBm, the RSSI can send a signal to the adjustable LNA 207 toincrease amplification in the adjustable LNA 207 by 5 dB. In variousembodiments, the RF RSSI 215 can be configured so that the determinedpreferred power value of the signal produced on the bypass path 201 inthe continuous feedback loop can be changed. For example, either throughuser input or through a decision made by logic incorporated in thedevice, the determined preferred power value of the signal afteramplification on the bypass path 201 in the device of the above examplemay be changed to −18 dBm instead of −20 dBm. In various embodiments,the determined preferred power value of the signal can be programmablethrough serial ports in the RF RSSI 215 through a SPI or an I2Cprotocol.

In an embodiment, the first stage LNA 204 on the main path 200 can be inbroadband, covering UHF and VHF bands. The input impedance of the LNA204 can be matched to the input, for example, the LNA 204 can be matchedto an antenna at 50 Ohms or 75 Ohms at the input. Moreover, this stagecan act as a single to differential converter to protect the signal fromthe common mode noise of the chip power supplies and ground (GND). Sincethe total noise figure (NF) of the tuner is highly dependent on the NFand gain of the first stage LNA 204, this stage can be designed to havea minimal NF, such as 2.5 dB. In order to reduce the noise introduced insubsequent stages, moderate gain, such as 18 dB, can be introduced inthe first stage LNA 204.

In various embodiments, the second stage LNA 205 on the main path 200and/or the first stage LNA 207 on the bypass path 201 can be a bufferwith adjustable attenuation of 1 dB to 30 dB. The LNAs 205, 207 can bedesigned to be substantially linear to handle high power signals. Aswill be illustrated in FIG. 3 and FIG. 4, to achieve high linearity andprogrammable gain, a differential attenuator made by several, forexample 12, parallel paths can be utilized in the LNAs 205, 207.

FIG. 3 shows an example of a buffer comprising an adjustable,substantially linear attenuator, in accordance with one embodiment. Thesecond LNA 205 on the main path 200 and/or the first LNA 207 on thebypass path 201 in FIG. 2 can contain such a buffer. The buffer mayinclude a substantially linear, programmable attenuator 300. In theexample illustrated, V.sub.dd 307 may be a power supply, V.sub.ip 306may be a positive input, V.sub.im 305 may be a negative input, R1 311may be a resistor, R2 304 may be a resistor, G1 310 and G2 309 may begrounds connections, VG0-VG11 301 may be control voltage signals thatcontrol the amount of attenuation in the attenuator 300, the terminalsV.sub.B1 and V.sub.B2 308, may be bias voltages, and V.sub.out “+” 302and V.sub.out “−” 303 may be differential outputs. The components may beelectronically connected as illustrated. In the example, the amount ofattenuation in the buffer is adjusted by controlling the amount ofattenuation in the attenuator 300 through 12 control voltage signalsVG0-VG11 301, which control voltage signals 301 can be conveyed fromother portions of the device such as, for example, an RSSI such as theRF-RSSI 215 in FIG. 2. In various embodiments, the buffer can contain asingle attenuator or several attenuators in series. Placing severalattenuators in series can improve characteristics such as linearity andsymmetry performance. An example of the attenuator 300 will be describedin further detail in FIG. 4, and an example of an RF RSSI 215 will bedescribed in further detail in FIGS. 7 and 8.

Because the signals conveyed to a buffer can be high power and thebuffer may need to be adjustable for a broad range of attenuation,building a suitable attenuator in the buffer can be challenging. Namely,because adjustable components, such as active resistors, have goodlinearity performance over only a limited range of resistance, buildingan attenuator that performs well over a broad range of signals ischallenging. To overcome this difficulty, in one embodiment, anattenuator can contain several parallel paths. The received signal canbe conveyed to a subset of the parallel paths within the attenuator. Forexample, a switch on each path can either open or close that path.Hence, by closing or opening corresponding switches, a determined subsetof paths for a desired amount of attenuation can be selected. Further,each path can be capable of producing different amounts of attenuation.For example, each path can contain a different resistor and produce adifferent amount of resistance. Further, the resistance on each path canbe variable, for example by implementing a variable resistor. In oneembodiment, each parallel path can contain an active resistor, such asan active resistor made by MOS transistors that act as MOS switches. Aswitch can be closed to select a corresponding path and opened tode-select it. Further, the switch can be modulated, that is, it can bemaintained between the closed and opened position to vary the amount ofresistance produced on the path.

FIG. 4 shows an example of an attenuator that can be contained in abuffer, in accordance with various embodiments. The second LNA 205 onthe main path 200 and/or the first LNA 207 on the bypass path 201 inFIG. 2 can comprise a buffer containing such an attenuator. Theillustrated attenuator can be an example of the attenuator 300 describedin FIG. 3. As FIG. 4 illustrates, a positive input of the attenuator,V.sub.ip 400, can be connected to a negative input of the attenuator,V.sub.im 401, by several, for example thirteen, parallel paths. Thepositive input V.sub.ip 400 and the negative input V.sub.im 401 can beconnections from the buffer, such as the connections to the attenuator300 in FIG. 3. From the top of the figure, the first path of theattenuator can contain a passive resistor 402. The second path cancontain an active resistor 402, such as an active resistor made by MOStransistors that act as MOS switches, which active resistor 402 can becontrolled by a first control signal, VG0, 403. The next path cancontain another active resistor 404 that can be controlled by a secondcontrol signal, VG1, 405. Similarly, the remaining 10 paths can eachcontain an active resistor that is controlled by a respective controlsignal. Control signals VG0 403 through VG11 can be the control signalsconveyed to the attenuator in the buffer, such as the signals VG0-VG11301 in FIG. 3. On each parallel path, the respective control signal canoperate to open or close an active resistor on the path. By controllingwhich resistors are opened and closed, the resistance between the inputs400, 401 can be adjusted. Further, the switches on the paths can bemodulated, that is, they can be maintained between the closed and openedposition to vary the amount of resistance produced on the path. Bymodulating switches, continuity in the level of attenuation can beachieved. Accordingly, the level of attenuation in the attenuator can becontrolled by the control signals VG0 to VG11.

The size and ordering of the active resistors in the attenuator can beselected to achieve a large range of adjustable attenuation whilemaintaining linearity. For example, the value of big resistors canincrease linearly while the values of small resistors can be binaryweighted. Hence, in various embodiments, the respective widths of thetransistors in the active resistors on the second to the thirteenthparallel path, respectively, can be: 0.5 W; 1 W; 1.5 W; 2 W; 3 W; 4 W; 6W; 9 W; 12 W; 18 W; 24 W; 48 W. Further, nonlinear components can becreated when an active resistor is between the open and closed position.Hence, to achieve substantial linearity, the system can be configured sothat at any given time most of the switches are in the open or closedposition and only 1 or 2 switches are between the open and closedposition. As will be described below, additional circuitry can be usedto generate the control signals VG0 to VG11 that control the activeresistors to achieve this. Further, such a circuit can be configured sothat the relationship between resistance and control voltage is linear.

The third stage LNA 206 on the main path 200 and the second stage LNA208 on the bypass path 201 in FIG. 2 can be linear voltage to currentconverters (transconductors) loaded with a band-pass filter (RF BPF) 217based on LC resonators. The RF BPF 217 can be primarily responsible forfar blocker rejection and can be programmable to cover a broadbandfrequency range by configuring several switched capacitors andinductors, for example six to eight switched capacitors can be used totune the RF BPF 217 in the UHF band. Since the impedance of the LCresonator will vary with frequency due to dependency of the resonator'squality factor (Q) on frequency, the input transconductance of thisstage can also be programmed to keep the gain flat over a desired range,such as 12-15 dB. In various embodiments, the RF BPF 217 and/or thetransconductors 206, 208 can be programmed through SPI (serial parallelinterface) or I2C protocol.

FIG. 5 is a flow-chart illustration of the process of RF signalamplification in a RF tuner, in accordance with various embodiments ofthe invention. The example of the process illustrated in the figure canbe applied in a configuration of components as illustrated in theexample of FIG. 2. As illustrated in FIG. 5, an incoming RF signal canbe received at the RF tuner 500. The signal can be amplified on a Mainpath 501 and the power of the RF signal can be measured 503 afteramplification to derive a power value (P). If the measured power valueis larger than a first defined threshold, then a decision 504 can bemade to perform further amplification of the RF signal on a Bypass Path509, which Bypass Path is capable of producing less amplification thanthe Main Path. As described in FIG. 2, in various embodiments, toproduce stability, switching between the Main and Bypass paths can bedelayed by using averaging, hysteresis, or other types of delayingand/or confirmation mechanisms. Otherwise, if the measured power islarger than a preferred power value, then a decision 505 can be made todecrease the amount of amplification on the Main Path 506 andamplification of subsequent RF signals can take place on the Main Path501 with decreased levels of amplification. Otherwise, if the measuredpower is smaller than a preferred power value, then a decision 507 canbe made to increase the amount of amplification on the Main Path 508 andamplification of subsequent RF signals can take place on the Main Path501 with increased levels of amplification. Otherwise, amplification ofsubsequent RF signals can take place on the Main Path 501 with unchangedlevels of amplification. With the signal being amplified on the Bypasspath, 509, the power of the RF signal can be measured 510 afteramplification to derive a power value (P). If the measured power valueis smaller than a second defined threshold, then a decision 511 can bemade to perform further amplification of the RF signal on the Main Path501. Otherwise, if the measured power is smaller than a preferred powervalue, then a decision 512 can be made to increase the amount ofamplification on the Bypass Path 513 and amplification of subsequent RFsignals can take place on the Bypass Path 509 with increased levels ofamplification. Otherwise, if the measured power is larger than apreferred power value, then a decision can be made 514 to decrease theamount of amplification on the Bypass Path 515 and amplification ofsubsequent RF signals can take place on the Bypass Path 509 withdecreased levels of amplification. Otherwise, amplification ofsubsequent RF signals can take place on the Bypass Path 509 withunchanged levels of amplification. The process can be performedcontinuously.

In various embodiments, the RF tuner can contain more than twoalternative paths for signal amplification. In that case, the system cancontain additional bypass switches and executable logic to route thesignal to either amplification path based on the signal power as will beapparent to a person of reasonable skill in the art in view of thisdisclosure. In another embodiment, the RF tuner can contain only asingle amplification path with a continuous feedback loop, as describedabove, on the path for adjusting amplification of RF signals on thepath. In other embodiments, the RF tuner can contain several paths, someor none of which can contain continuous feedback loops, as describedabove, for adjusting amplification of RF signals on the relative path.

FIG. 6 shows an example of a power detector, in accordance with variousembodiments. The power detectors PD1 209, PD2 210, and/or PD3 218 inFIG. 2 can include architecture of the illustrated example. In theexample illustrated, a power detector can receive an incoming signal 600and produce a power detection signal V.sub.0-PD 609. Bias Circuitry 603can produce a signal of a fixed voltage and convey that signal to tworoot-mean-square (RMS) Detectors 604, 605. The incoming signal 600 canbe conveyed to a first LNA 601, to a second LNA 602, and to an RMSDetector 604. The signals from the RMS power detectors 604, 605 can beconveyed to an amplifier 608. The signal from the RMS Detector 604 canbe conveyed to a capacitor 606 and a ground connection 607. The powerdetection signal V.sub.0-PD 609 can be produced in the amplifier 608.The components may be electronically connected as illustrated. From thepower detector, the power detection signal V.sub.0-PD 609 can beconveyed to other components, such as a RSSI.

FIG. 7 shows an example of a radio frequency RSSI in accordance with oneembodiment. The RF-RSSI 215 of FIG. 2 can contain architecture of theillustrated example. In the example illustrated, V.sub.0-PD 702 can be apower detection signal received from a power detector, such as theV.sub.0-PD 609 power detection signal in FIG. 6; Programming signal 700can be an 8 bit digital input signal from a SPI (serial parallelinterface) or I2C protocol; DAC 701 can be a digital to analogconverter; Amp 703 can be an amplifier; LPF 704 can be a low-passfilter; V.sub.c 706 can be a produced analog control voltage signal; andControl Signal Generator 705 can be a unit that processes the analogcontrol voltage signal V.sub.c 706 to produce 12 control voltage signalsVG0 to VG11 707. The components may be electronically connected asillustrated. The 12 control voltage signals VG0 to VG11 707 can beconveyed to other components to control the respective components. Forexample, the control voltage signals VG0 to VG11 707 can be conveyed tocorresponding active resistors in an attenuator as shown in FIG. 4,which attenuator can be contained in a buffer 205, 207 as illustrated inFIG. 2, to set the level of attenuation in the corresponding buffers. Anexample of the Control Signal Generator 705 will be described in furtherdetail in FIG. 8.

The analog control voltage signal V.sub.c 706 can change in a linearrelationship with the power detection signal V.sub.0-PD 702. The powerdetection signal V.sub.0-PD 702 can be compared to the reference voltageconveyed from the DAC 701 in the amplifier 703; filtering in the lowpass filter 704 can generate the analog control voltage signal V.sub.c706. The reference voltage can be precisely generated by the 8 bit DAC701. The DAC 701 can be controlled by an SPI or I2C protocol. Hence, thedigital programming signal 700 coming from the SPI or I2C protocol canprogram the DAC 701 to set the power of a signal that is produced in afeedback loop containing the illustrated radio frequency RSSI. Forexample, if the RSSI is implemented in a configuration as illustrated inFIG. 2, because the power detector 218 measures signal power after theLNAs 208, 206, the RF-RSSI 215 can be programmed to fix the output powerof the LNAs 208, 206 at a defined value by programming the DAC 701through the SPI or I2C protocol.

In another embodiment, the RSSI can be non-programmable. In that case,instead of the reference voltage from the DAC 701, a fixed voltage canbe conveyed to the positive input of the amplifier 703 to be compared inthe amplifier 703 with the power detection signal V.sub.0-PD 702.

As described above, the attenuation in buffers, such as the buffers 205,208 in FIG. 2, can be implemented through 12 active resistorsincorporated in the respective buffer. An example of such a buffer withactive resistors is illustrated in FIG. 4. An RSSI, such as one asdescribed in FIG. 7, can produce control voltage signals VG0 to VG11 707to control the respective active resistors and thereby set the level ofattenuation in a buffer. A Control Signal Generator 705 in an RSSI canprocess the analog control voltage signal V.sub.c 706 to produce 12control voltage signals VG0 to VG11 707.

FIG. 8 shows an example of a control signal generator in accordance withvarious embodiments. The described control signal generator can be anexample of the Control Signal Generator 705 in the RSSI illustrated inFIG. 7. The control signal generator can receive an analog controlvoltage signal V.sub.c 806 and produce 12 control voltage signals VG0804 to VG11 811 that can be conveyed to 12 corresponding activeresistors in another component, such as the active resistors of theattenuator in the buffer 205, 207 in FIG. 2, to control a function ofthat component, such as the amount of attenuation produced in thebuffer. In the example illustrated, V.sub.dd 800 is a positive powersupply; RH 801 is a resistor; R 802 is a resistor; V.sub.F0 808 is afixed voltage; V.sub.c 806 is an analog control voltage signal receivedat the control signal generator; V.sub.c 806 and V.sub.F0 808 can beconveyed to a low speed comparator 803; VG0 804 is a produced controlvoltage signal; RL 807 is a resistor; and G 805 is a ground connection.The components may be electronically connected as illustrated.

For the sake of simplicity, only four comparators and correspondingcomponents are illustrated in FIG. 8. The remaining eight comparatorsand the corresponding resistors, input analog control voltages(V.sub.c), fixed voltages, and produced control signals are omittedbecause their illustration is identical. Namely, after the thirdcomparator 809, another resistor can be connected in series with thepath, the resistor can be followed by a fourth comparator, which canproduce a control voltage signal VG3, another resistor can follow thefourth comparator, and so on until the twelfth comparator 810, which cangenerate the control voltage signal VG11 811. The twelfth comparator canbe followed by the resistor RL 807, which resistor can be followed bythe ground connection G 805. Each comparator producing control voltagesignals VG0 804 through VG11 811 can receive an identical analog controlvoltage signal V.sub.c 806 and a different corresponding fixed voltagesignal V.sub.F0 808 through V.sub.F11 812, respectively. Hence, togenerate the twelve control voltage signals VG0 804 to VG11 811 in thecontrol signal generator, the input analog control voltage V.sub.c iscompared to 12 fixed voltages V.sub.F0 808 through V.sub.F11 812 in 12low speed comparators.

Stability of feedback loops can be optimized by providing a dominantpole in the feedback loop; for example, the low pass filter 704 of FIG.7 can produce the dominant pole of the corresponding feedback loop. Byadjusting the low pass filter 704, the loop can work with highlyfluctuating signals, such as signals with fluctuations caused by fadingor Doppler effects, as can occur in mobile applications.

In various embodiments, incoming RF signals across a wide range ofpowers can be amplified to produce continuous signals of a fixed,desired power while maintaining other desirable signal characteristicssuch as noise and linearity. Namely, by using a main path configured foroptimal amplification of low power incoming RF signals and a bypass pathconfigured for optimal amplification of high power incoming RF signals,as described in above embodiments, with continuous feedback loops tofurther adjust amplification when the signal is routed to either pathsignals of both extremely weak power and extremely strong power can beamplified to produce a signal with continuously stable and desirablepower in addition to other favorable signal characteristics such asnoise and linearity.

In various embodiments, undesirable low and/or high frequencies can befiltered from a received RF signal or a previously amplified received RFsignal, the filtering can be performed in a band-pass filter, forexample. The signal can be converted from voltage to current in atransconductor, which transconductor may be able to produce adjustablegain. The signal can be amplified with variable levels of amplification.The signal can be amplified during, before, and/or after the voltage tocurrent conversion with variable amounts of amplification. The signalcan be down converted to a low frequency, such as an intermediate or abaseband frequency. An in-phase signal component and a quadrature-phasesignal component of the signal can be produced. Undesirable frequenciescan be filtered from the down-converted signal. The power of theproduced signal can be measured and adjusted by varying the amount ofamplification in the amplifying components, which adjustment can bebased on the measured signal power, according to a defined logicincorporated into the device. Both the adjustment of amplification andthe signal power measurement can be continuous.

In various embodiments, a RF signal can be conveyed to a RF band-passfilter. Any systems that control the amount of amplification of the RFsignal can be configured so that the RF signal is amplified to reach apredefined preferred power prior to being conveyed to the band-passfilter. After being filtered in the band-pass filter, the RF signal canbe conveyed to a transconductor with adjustable gain, where the signalcan be converted from voltage to current. After the signal is convertedto current in the transconductor and amplified, the signal can beconveyed to a mixer or quadrature switches, where the signal can betransferred to a lower frequency such as baseband or intermediatefrequency (IF), and/or where I and Q signal components of the signal canbe produced. The produced signal or produced I and Q signal componentscan be passed through a low-pass filter. The power of the producedsignal or produced I and Q signal components can be adjusted through acontinuous feedback loop wherein the power of the signal or one or bothof the I and Q signal components can be measured and the gain in thetransconductor can be adjusted based on the measured signal poweraccording to defined logic incorporated in the device.

As described above, a signal can be conveyed to a set of componentswhere the signal can be down converted to low frequencies and undesiredfrequencies can be removed from the signal by filtering. The incomingsignal can be a signal that has been received at the RF receiver andamplified, which amplification can take place in a configuration ofcomponents as illustrated in FIG. 2. A continuous feedback loop can beused to fix the power of the produced low frequency signal.

FIG. 9 shows an example of a configuration of components for downconverting a RF signal and fixing the power of a produced low frequencysignal, in accordance with various embodiments of the invention. Theincoming RF signal can be a signal that has been received at the RFreceiver, amplified in an amplifier stage, and filtered in a band-passfilter, all of which can take place in a configuration of components asillustrated in FIG. 2. The signal can be conveyed to a transconductor(Gm) 918, which can convert the signal from voltage to current andamplify the signal with adjustable amounts of gain. In an embodiment,the amplification in the transconductor 918 can be varied, for example,the gain can vary by 30 dB. After the transconductor 918, the signal canbe conveyed down an in-phase (I) path and a quadrature-phase (Q) path.The signal can be down converted to intermediate frequencies (IF) in aquadrature switch 919 on the I path and a quadrature switch 920 on the Qpath. The quadrature switches can be driven by a synthesizer 921. Thesignal on the I path can be conveyed to a low-pass filter 922, which canbe a first order RC active filter, and the signal on the Q path can beconveyed to another low-pass filter 923, which can also be a first orderRC active filter. In various embodiments, the total amplification of thesignal in the transconductor 918 and the active low pass filter 922, 923together can be 24 dB.

In various embodiments, a continuous feedback loop can be used to fixthe power of a signal produced on the I path 927 and a signal producedon the Q path 928. For example, the signal produced on the I path 927can be conveyed to a IF RSSI 924. The signal power can be measured andthe signal's power can be adjusted by changing the amount ofamplification in the transconductor 918 based on the measured signalpower according to executable logic incorporated in the IF RSSI 924. Invarious embodiments, the signal power can be measured by a powerdetector located in the IF RSSI 924 or in a power detector locatedbefore the IF RSSI 924. The adjustment of amplification can be performedcontinuously. It should be noted that the power of the signal producedon the I path and the Q path can be identical and that by changing theamplification produced in the transconductor 918, the power of thesignal produced on both the I path and the Q path can changedidentically; hence, to fix the power of both the produced I signal 927and produced Q signal 928, it can be enough to measure the signal poweron one of the I and Q paths and adjust the amplification produced in thetransconductor 918 respectively. Thus, the corresponding components andfunctions described here as being performed on the I path can similarlybe performed on the Q path and vice versa. In one embodiment, the signalpower can be measured using continuous IF power measurement. The signalcan be measured in the IF RSSI 924 or the signal can be measured inanother component and the measured signal power value can be conveyed tothe IF RSSI 924. Hence, in various embodiments, the IF RSSI 924 can beconfigured so that the power of the signal produced on the I path 927and the power of the signal produced on the Q path 928 is a fixedpreferred value. For example, the continuous feedback loop can beconfigured so that the determined preferred value of the signal on the Ipath 927 is −10 dBm. In that case, if the IF RSSI 924 measures that thepower of the produced signal is −5 dBm, the IF RSSI 924 can send asignal to the adjustable transconductor 918 to decrease amplification inthe adjustable transconductor 918 by 5 dB. Similarly, if the IF RSSI 924measures that the produced signal's power is −15 dBm, the IF RSSI 924can send a signal to the adjustable transconductor 918 to increaseamplification in the adjustable transconductor 918 by 5 dB. In variousembodiments, the IF RSSI 924 can be configured so that the determinedpreferred value of the signal power produced on the I path 927 in thecontinuous feedback loop can be changed. For example, either throughuser input or through a decision made by logic incorporated in thedevice, the determined preferred value of the signal power afteramplification on the I path in the device of the above example may bechanged to −15 dBm instead of −10 dBm. In various embodiments, thedetermined preferred value of the signal power can be programmablethrough serial ports in the IF RSSI 924 through a SPI or I2C protocol.In various embodiments, to avoid creating an imbalance in signalcharacteristics between the signals on the I path and the Q path, thesignal on the Q path can be conveyed to a IF RSSI 925 so that the loadon the Q path is matched to the load on the I path.

Generally, the signal received at the transconductor 918 can containundesirable components, such as blockers, adjacent channels, and noise,which undesirable components may be of significantly higher power thanthe desired component of the signal and hence are preferably removedbefore the signal power is measured for adjusting the level ofamplification in the transconductor. In various embodiments, aftervoltage to current conversion and amplification in the transconductor918, the signal can be conveyed to quadrature switches 919, 920 and tolow pass filters 922, 923 to remove undesirable signal components andproduce a desired signal. The IF RSSI 924 can measure the power of thedesired signal and fix it at a preferred power value by adjusting thegain in the transconductor 918 based on the measured power of thedesired signal, according to executable logic incorporated in the IFRSSI 924. Thus, the method and system can produce a desired signalcomponent of a fixed, preferred power while eliminating undesirablecomponents.

FIG. 10 is a flow-chart illustration of the process of down converting aRF signal and fixing the power of a produced low frequency signal, inaccordance with various embodiments of the invention. As illustrated inFIG. 4, a RF signal can be received 1000 and the signal can be filteredin a bandpass filter 1001. The RF signal can be converted from voltageto current in a transconductor 1002. The signal's power can be amplifiedin the transconductor 1003 with a variable level of amplification. Thesignal can be down converted to low frequencies, such as intermediate orbaseband frequencies, in a mixer or quadrature switches 1004. Undesiredfrequencies can be filtered from the signal in a low pass filter 1005.The power of the signal can be measured to derive a power value (P)1006. If the power value (P) is larger than a preferred value, then adecision 1007 can be made to decrease the amount of amplification in thetransconductor 1008 and amplification of subsequent signals in thetransconductor 1003 can be performed with the decreased levels ofamplification. Otherwise, if P is smaller than preferred, then adecision 1009 can be made to increase the amount of amplification in thetransconductor 1010 and amplification of subsequent signals in thetransconductor 1003 can be performed with the increased levels ofamplification. Otherwise, amplification of subsequent signals in thetransconductor 1003 can be performed with unchanged levels ofamplification.

FIG. 11 shows an example of a transconductor comprising a substantiallylinear attenuator in accordance with various embodiments. In the exampleillustrated, V.sub.dd 1100 can be a positive power supply; Load+CMFB1101 can be a common mode feedback and load; V.sub.ip can be a positiveinput; V.sub.im 1103 can be a negative input; Output 1104 can be adifferential output; R 1105 can be a resistor; Attenuators 1107 and 1108can be substantially linear attenuators; 12 Control signals 1106 can becontrol voltage signals conveyed to the attenuators to controlattenuation in the transconductor, for example, the 12 control signalscan come from an RSSI such as the IF RSSI 317 in FIG. 3; V.sub.B1 andV.sub.B2 1109 can be a fixed voltage bias; G1 1110 can be a ground; andG2 1111 can be a ground. The components may be electronically connectedas illustrated. In various embodiments, the transconductor can produce30 dB of programmable attenuation range.

Because the input signal at the transconductor can be high power and cancontain powerful blockers, it can be desirable to implement a highlylinear transconductor to meet the required SNDR. Moreover, it can bedesirable for the gain in the transconductor to be programmable.Linearity and programmability can be achieved by implementing a highlylinear, programmable attenuator in the transconductor. For example, inthe transconductor illustrated in the example of FIG. 11, theattenuators 1107 and 1108 can comprise highly linear, programmableattenuators. In various embodiments, the transconductor can contain asingle attenuator or several attenuators in series, such as twoattenuators in series as illustrated in FIG. 11. Placing severalattenuators in series can improve characteristics such as linearity andsymmetry performance. In an embodiment, the architecture of theattenuator(s) can be similar to the architecture of the attenuatordescribed in FIG. 4. The level of attenuation in the attenuator and thelevel of gain in the transconductor can be controlled by an RSSI, suchas the IF RSSI 924 in FIG. 9. For example, the RSSI can send controlvoltage signals to the active resistors contained in the attenuators inthe transconductor(s). The architecture of the RSSI can be similar tothe architecture of the RSSI described in FIG. 7.

In various embodiments, a first portion of the RF tuner can comprise aconfiguration of LNAs, continuous feedback loops, and bypass paths, asdescribed by example in FIG. 2, for receiving incoming RF signals in awide range of powers and producing RF signals of a fixed preferred powerwith desirable signal characteristics. A second portion of the RF tunercan comprise a configuration of components for down converting thesignal to a low frequency, filtering undesired components out of thesignal, and amplifying the signal in a continuous feedback loop toproduce a low frequency signal with a fixed preferred power and otherdesirable characteristics, as described by example in FIG. 9.

FIG. 12 shows an example of a RF tuner with a portion where RF signalsin a broad range of powers can be amplified to produce RF signals of afixed preferred power and a portion where RF signals can be downconverted, filtered to remove undesired components, and amplified toproduce a low frequency signal with a fixed preferred power, inaccordance with one embodiment. As illustrated in FIG. 12, incoming RFsignals 1203 can be received in the RF tuner 1200. The RF signals 1203can be in a broad range of powers. The RF signals 1203 can be conveyedto a first set of components 1201, which first set of components cancomprise continuous feedback loops and bypass paths that performamplification of the RF signals to produce RF signals of a fixed powerwith other desirable characteristics. The signal can then be conveyed toa second set of components 1202, where the signal can be down converted,filtered to remove undesired components, and amplified to produce anin-phase 1204 low frequency signal component of a fixed preferred powerand a quadrature-phase 1205 low frequency signal component of a fixedpreferred power.

While certain exemplary embodiments have been described and shown in theaccompanying drawings, it is to be understood that such embodiments aremerely illustrative of and not restrictive on the broad invention, andthat this invention is not limited to the specific constructions andarrangements shown and described, since various other modifications mayoccur to those ordinarily skilled in the art. Hence, alternativearrangements and/or quantities of amplifiers, bypass switches, RSSIs,power detectors, transmission paths, and other components can occurwithout departing from the spirit and scope of the invention. Similarly,components not explicitly mentioned in this specification can beincluded in various embodiments of this invention without departing fromthe spirit and scope of the invention. Also, functions and logicdescribed as being performed in certain components in variousembodiments of this invention can, as would be apparent to one skilledin the art, be readily performed in whole or in part in differentcomponents or in different configurations of components not explicitlymentioned in this specification, without departing from the spirit andscope of the invention. Accordingly, the specification and drawings areto be regarded in an illustrative rather than a restrictive sense.

While certain exemplary embodiments have been described and shown in theaccompanying drawings, it is to be understood that such embodiments aremerely illustrative of and not restrictive on the broad invention, andthat this invention is not limited to the specific constructions andarrangements shown and described, since various other modifications mayoccur to those ordinarily skilled in the art. Accordingly, thespecification and drawings are to be regarded in an illustrative ratherthan a restrictive sense.

Reference in the specification to “an embodiment,” “one embodiment,”“some embodiments,” “various embodiments” or “other embodiments” meansthat a particular feature, structure, or characteristic described inconnection with the embodiments is included in at least someembodiments, but not necessarily all embodiments. References to “anembodiment,” “one embodiment,” or “some embodiments” are not necessarilyall referring to the same embodiments. If the specification states acomponent, feature, structure, or characteristic “may,” “can,” “might,”or “could” be included, that particular component, feature, structure,or characteristic is not required to be included. If the specificationor Claims refer to “a” or “an” element, that does not mean there is onlyone of the element. If the specification or Claims refer to an“additional” element, that does not preclude there being more than oneof the additional element.

What is claimed is:
 1. A method for processing a RF signal in a RFreceiver, comprising: receiving the RF signal at the RF receiver;attenuating the RF signal in a component with an adjustable level ofattenuation; measuring the power of the signal; and adjusting the levelof attenuation in the component in an analog feedback loop based on themeasured power.